MC33077

http://onsemi.com

11

APPLICATIONS INFORMATION

The MC33077 is designed primarily for its low noise, low

offset voltage, high gain bandwidth product and large output

swing characteristics. Its outstanding high frequency

gain/phase performance make it a very attractive amplifier for

high quality preamps, instrumentation amps, active filters and

other applications requiring precision quality characteristics.

The MC33077 utilizes high frequency lateral PNP input

transistors in a low noise bipolar differential stage driving a

compensated Miller integration amplifier. Dual−doublet

frequency compensation techniques are used to enhance the

gain bandwidth product. The output stage uses an all NPN

transistor design which provides greater output voltage

swing and improved frequency performance over more

conventional stages by using both PNP and NPN transistors

(Class AB). This combination produces an amplifier with

superior characteristics.

Through precision component matching and innovative

current mirror design, a lower than normal temperature

coefficient of input offset voltage (2.0

mV/°C as opposed to

10

mV/°C), as well as low input offset voltage, is accomplished.

The minimum common mode input range is from 1.5 V

1.0 V of both negative and positive rails though degradation

in offset voltage and gain will be experienced as the common

mode voltage nears either supply rail. In practice, though not

approximately 0.6 V without causing permanent damage to

the device. If the input voltage on either or both inputs is less

than approximately 0.6 V, excessive current may flow, if not

limited, causing permanent damage to the device.

The amplifier will not latch with input source currents up

to 20 mA, though in practice, source currents should be

limited to 5.0 mA to avoid any parametric damage to the

high state and phase reversal may occur. No phase reversal

will occur if the voltage on one input is within the common

Phase reversal may occur if the input voltage on either or

both inputs is less than 1.0 V above the negative rail. Phase

reversal will be experienced if the voltage on either or both

Through the use of dual−doublet frequency compensation

techniques, the gain bandwidth product has been greatly

enhanced over other amplifiers using the conventional

single pole compensation. The phase and gain error of the

amplifier remains low to higher frequencies for fixed

amplifier gain configurations.

With the all NPN output stage, there is minimal swing loss

to the supply rails, producing superior output swing, no

crossover distortion and improved output phase symmetry

with output voltage excursions (output phase symmetry

being the amplifiers ability to maintain a constant phase

relation independent of its output voltage swing). Output

phase symmetry degradation in the more conventional PNP

and NPN transistor output stage was primarily due to the

inherent cut−off frequency mismatch of the PNP and NPN

transistors used (typically 10 MHz and 300 MHz,

respectively), causing considerable phase change to occur as

the output voltage changes. By eliminating the PNP in the

output, such phase change has been avoided and a very

significant improvement in output phase symmetry as well

as output swing has been accomplished.

The output swing improvement is most noticeable when

operation is with lower supply voltages (typically 30% with

± 5.0 V supplies). With a 10 k load, the output of the

amplifier can typically swing to within 1.0 V of the positive

voltage swing can be further improved by using an output

are referenced to the positive supply rail, the pull−up resistor

during the negative swing, the NPN output transistor

configuration will produce the maximum attainable output

signal from given supply voltages. The value of load

resistance used should be much less than any feedback

resistance to avoid excess loading and allow easy pull−up of

the output.

Output impedance of the amplifier is typically less than

50

W at frequencies less than the unity gain crossover

frequency (see Figure 19). The amplifier is unity gain stable

with output capacitance loads up to 500 pF at full output

swing over the −55

° to +125°C temperature range. Output

phase symmetry is excellent with typically 4

°C total phase

change over a 20 V output excursion at 25

°C with a 2.0 kW

and 100 pF load. With a 2.0 k

W resistive load and no

capacitance loading, the total phase change is approximately

one degree for the same 20 V output excursion. With a

2.0 k

W and 500 pF load at 125°C, the total phase change is

typically only 10

°C for a 20 V output excursion (see

Figure 28).

As with all amplifiers, care should be exercised to insure

that one does not create a pole at the input of the amplifier

which is near the closed loop corner frequency. This becomes

a greater concern when using high frequency amplifiers since

it is very easy to create such a pole with relatively small values

of resistance on the inputs. If this does occur, the amplifier’s

phase will degrade severely causing the amplifier to become

unstable. Effective source resistances, acting in conjunction

with the input capacitance of the amplifier, should be kept to

a minimum to avoid creating such a pole at the input (see

Figure 32). There is minimal effect on stability where the

created input pole is much greater than the closed loop corner

frequency. Where amplifier stability is affected as a result of

a negative feedback resistor in conjunction with the